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PDF MAX4266 Data sheet ( Hoja de datos )
| Número de pieza | MAX4266 | |
| Descripción | Ultra-Low-Distortion / Single-Supply / 300MHz Op Amps with Enable | |
| Fabricantes | Maxim Integrated | |
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19-1552; Rev 0; 10/99
Ultra-Low-Distortion, Single-Supply,
300MHz Op Amps with Enable
General Description
The MAX4265–MAX4270 single-supply, voltage-feedback
op amps are capable of driving a 100Ω load while main-
taining ultra-low distortion over a wide bandwidth. They
offer superior spurious-free dynamic range (SFDR) perfor-
mance: -90dBc or better at frequencies below 5MHz and
-60dBc at a 100MHz frequency. Additionally, input voltage
noise density is 8nV/√Hz while operating from a single
+4.5V to +8.0V supply or from dual ±2.25V to ±4.0V sup-
plies. These features make the MAX4265–MAX4270 ideal
for use in high-performance communications and signal-
processing applications that require low distortion and
wide bandwidth.
The MAX4265 single and MAX4268 dual unity-gain-stable
amplifiers have up to a 300MHz gain-bandwidth product.
The MAX4266 single and MAX4269 dual amplifiers have
up to a 350MHz bandwidth at a minimum stable gain of
+2V/V. The MAX4267 single and MAX4270 dual amplifiers
have a 200MHz bandwidth at a minimum stable gain of
+5V/V.
For additional power savings, these amplifiers feature a
low-power disable mode that reduces supply current to
1.6mA and places the outputs in a high-impedance state.
The MAX4265/MAX4266/MAX4267 are available in a
space-saving 8-pin µMAX package, and the MAX4268/
MAX4269/MAX4270 are available in a 16-pin QSOP pack-
age.
Applications
Base-Station Amplifiers
IF Amplifiers
High-Frequency ADC Drivers
High-Speed DAC Buffers
RF Telecom Applications
High-Frequency Signal Processing
Pin Configurations appear at end of data sheet.
Selector Guide
PART
MAX4265
MAX4266
MAX4267
MAX4268
MAX4269
MAX4270
NO. OF
OP AMPS
1
1
1
2
2
2
MIN GAIN
(V/V)
1
2
5
1
2
5
BANDWIDTH
(MHz)
300
350
200
300
350
200
Features
o +4.5V to +8.0V Single-Supply Operation
o Superior SFDR with 100Ω Load
-90dBc (fC = 5MHz )
-60dBc (fC = 100MHz)
o 35dBm IP3 (fC = 20MHz)
o 8nV/√Hz Voltage Noise Density
o 100MHz 0.1dB Gain Flatness (MAX4268)
o 900V/µs Slew Rate
o ±45mA Output Driving Capability
o Shutdown Mode Places Outputs in High-
Impedance State
Ordering Information
PART
MAX4265EUA*
MAX4265ESA*
MAX4266EUA*
MAX4266ESA*
MAX4267EUA*
TEMP. RANGE
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
PIN-PACKAGE
8 µMAX
8 SO
8 µMAX
8 SO
8 µMAX
MAX4267ESA*
MAX4268EEE
MAX4268ESD
MAX4269EEE
MAX4269ESD
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
8 SO
16 QSOP
14 SO
16 QSOP
14 SO
MAX4270EEE
-40°C to +85°C 16 QSOP
MAX4270ESD
-40°C to +85°C 14 SO
*Future product—contact factory for availability.
SFDR vs. Input Frequency
-20
VOUT = 1Vp-p
-30 RL = 100Ω to VCC/2
-40
-50
-60
MAX4270
-70
-80 MAX4269
-90
-100
0.1M
MAX4268
1M 10M
FREQUENCY (Hz)
100M
________________________________________________________________ Maxim Integrated Products 1
For free samples & the latest literature: http://www.maxim-ic.com, or phone 1-800-998-8800.
For small orders, phone 1-800-835-8769.
1 page  
Ultra-Low-Distortion, Single-Supply,
300MHz Op Amps with Enable
Typical Operating Characteristics (continued)
(VCC = +5V, VEE = 0, EN_ = 5V, RL = 100Ω to VCC/2, MAX4268 AV = +1V/V, MAX4269 AV = +2V/V, MAX4270 AV = +5V/V, TA =+25°C,
unless otherwise noted.)
MAX4268
DISTORTION vs. FREQUENCY
-20
VOUT = 1Vp-p
-30
MAX4269
DISTORTION vs. FREQUENCY
-20
VOUT = 1Vp-p
-30
MAX4270
DISTORTION vs. FREQUENCY
-20
VOUT = 1Vp-p
-30
-40 -40
-40
-50 -50
-60 -60
-50
-60
-70
-80
-90
-100
0.1M
2ND HARMONIC
3RD HARMONIC
1M 10M
FREQUENCY (Hz)
100M
-70
2ND HARMONIC
-80 3RD HARMONIC
-90
-100
0.1M
1M 10M
FREQUENCY (Hz)
100M
-70
-80 2ND HARMONIC
-90 3RD HARMONIC
-100
0.1M
1M 10M
FREQUENCY (Hz)
100M
MAX4268
DISTORTION vs. LOAD
-20
fO = 5MHz
-30 VOUT = 1Vp-p
-40
-50
-60
-70
-80
-90
-100
0
2ND HARMONIC
3RD HARMONIC
100 200 300 400 500
RESISTIVE LOAD (Ω)
600
MAX4269
DISTORTION vs. LOAD
-20
fO = 5MHz
-30 VOUT = 1Vp-p
-40
-50
-60
-70
-80 2ND HARMONIC
-90
-100
0
3RD HARMONIC
100 200 300 400 500 600
RESISTIVE LOAD (Ω)
MAX4270
DISTORTION vs. LOAD
-20
fO = 5MHz
-30 VOUT = 1Vp-p
-40
-50
-60
-70
-80 2ND HARMONIC
-90
-100
0
3RD HARMONIC
100 200 300 400 500
RESISTIVE LOAD (Ω)
600
MAX4268
DISTORTION vs. VOLTAGE SWING
-20
fO = 5MHz
-30
-40
-50
-60
-70
2ND HARMONIC
-80
-90
-100
0
3RD HARMONIC
0.5 1.0 1.5 2.0
VOLTAGE SWING (Vp-p)
2.5
MAX4269
DISTORTION vs. VOLTAGE SWING
-20
fO = 5MHz
-30
-40
-50
-60
-70
2ND HARMONIC
-80 3RD HARMONIC
-90
-100
0
0.5 1.0 1.5 2.0
VOLTAGE SWING (Vp-p)
2.5
MAX4270
DISTORTION vs. VOLTAGE SWING
-20
fO = 5MHz
-30
-40
-50
-60
-70
2ND HARMONIC
-80
-90 3RD HARMONIC
-100
0
0.5 1.0 1.5 2.0
VOLTAGE SWING (Vp-p)
2.5
_______________________________________________________________________________________ 5
5 Page 
Ultra-Low-Distortion, Single-Supply,
300MHz Op Amps with Enable
Choosing Resistor Values
Unity-Gain Configurations
The MAX4265 and MAX4268 are internally compensat-
ed for unity gain. When configured for unity gain, they
require a small resistor (RF) in series with the feedback
path (Figure 1). This resistor improves AC response by
reducing the Q of the tank circuit, which is formed by
parasitic feedback inductance and capacitance.
Inverting and Noninverting Configurations
The values of the gain-setting feedback and input resis-
tors are important design considerations. Large resistor
values will increase voltage noise and interact with the
amplifier’s input and PC board capacitance to generate
undesirable poles and zeros, which can decrease
bandwidth or cause oscillations. For example, a nonin-
verting gain of +2V/V (Figure 1) using RF = RG = 1kΩ
combined with 2pF of input capacitance and 0.5pF of
board capacitance will cause a feedback pole at
128MHz. If this pole is within the anticipated amplifier
bandwidth, it will jeopardize stability. Reducing the 1kΩ
resistors to 100Ω extends the pole frequency to
1.28GHz, but could limit output swing by adding 200Ω
in parallel with the amplifier’s load. Clearly, the selec-
tion of resistor values must be tailored to the specific
application.
Distortion Considerations
The MAX4265–MAX4270 are ultra-low-distortion, high-
bandwidth op amps. Output distortion will degrade as
the total load resistance seen by the amplifier decreas-
es. To minimize distortion, keep the input and gain-set-
ting resistor values relatively large. A 500Ω feedback
resistor combined with an appropriate input resistor to
set the gain will provide excellent AC performance with-
out significantly increasing distortion.
Noise Considerations
The amplifier’s input-referred noise-voltage density is
dominated by flicker noise at lower frequencies and by
thermal noise at higher frequencies. Because the ther-
mal noise contribution is affected by the parallel combi-
nation of the feedback resistive network, those resistor
values should be reduced in cases where the system
bandwidth is large and thermal noise is dominant. This
noise-contribution factor decreases, however, with
increasing gain settings. For example, the input noise
voltage density at the op amp input with a gain of
+10V/V using RF = 100kΩ and RG = 11kΩ is en =
18nV/√Hz. The input noise can be reduced to 8nV/√Hz
by choosing RF = 1kΩ, RG = 110Ω.
Driving Capacitive Loads
The MAX4265–MAX4270 are not designed to drive
highly reactive loads; stability is maintained with loads
up to 15pF with less than 2dB peaking in the frequency
response. To drive higher capacitive loads, place a
small isolation resistor in series between the amplifier’s
output and the capacitive load (Figure 1). This resistor
improves the amplifier’s phase margin by isolating the
capacitor from the op amp’s output.
To ensure a load capacitance that limits peaking to less
than 2dB, select a resistance value from Figure 2. For
example, if the capacitive load is 100pF, the corre-
sponding isolation resistor is 6Ω (MAX4269). Figures 3
and 4 show the peaking that occurs in the frequency
response with and without an isolation resistor.
Coaxial cable and other transmission lines are easily
driven when terminated at both ends with their charac-
teristic impedance. When driving back-terminated
transmission lines, the capacitive load of the transmis-
sion line is essentially eliminated.
ADC Input Buffer
Input buffer amplifiers can be a source of significant
errors in high-speed ADC applications. The input buffer
is usually required to rapidly charge and discharge the
ADC’s input, which is often capacitive (see Driving
Capacitive Loads). In addition, since a high-speed
ADC’s input impedance often changes very rapidly dur-
ing the conversion cycle, measurement accuracy must
RG RF
RS*
VIN
PART
MAX4265
MAX4266
MAX4267
MAX4265
MAX4266
MAX4267
CL
RF (Ω)
24
500
500
RG (Ω)
∞
500
125
GAIN (V/V)
1
2
5
RL
*OPTIONAL, USED TO MINIMIZE PEAKING FOR CL > 15pF.
Figure 1. Noninverting Configuration
______________________________________________________________________________________ 11
11 Page | ||
| Páginas | Total 16 Páginas | |
| PDF Descargar | [ Datasheet MAX4266.PDF ] | |
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