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PDF MC33035 Data sheet ( Hoja de datos )
| Número de pieza | MC33035 | |
| Descripción | BRUSHLESS DC MOTOR CONTROLLER | |
| Fabricantes | Motorola Semiconductors | |
| Logotipo |  |
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Hay una vista previa y un enlace de descarga de MC33035 (archivo pdf) en la parte inferior de esta página. Total 24 Páginas | ||
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MC33035
Brushless DC
Motor Controller
The MC33035 is a high performance second generation monolithic
brushless DC motor controller containing all of the active functions required
to implement a full featured open loop, three or four phase motor control
system. This device consists of a rotor position decoder for proper
commutation sequencing, temperature compensated reference capable of
supplying sensor power, frequency programmable sawtooth oscillator, three
open collector top drivers, and three high current totem pole bottom drivers
ideally suited for driving power MOSFETs.
Also included are protective features consisting of undervoltage lockout,
cycle–by–cycle current limiting with a selectable time delayed latched
shutdown mode, internal thermal shutdown, and a unique fault output that
can be interfaced into microprocessor controlled systems.
Typical motor control functions include open loop speed, forward or
reverse direction, run enable, and dynamic braking. The MC33035 is
designed to operate with electrical sensor phasings of 60°/300° or
120°/240°, and can also efficiently control brush DC motors.
• 10 to 30 V Operation
• Undervoltage Lockout
• 6.25 V Reference Capable of Supplying Sensor Power
• Fully Accessible Error Amplifier for Closed Loop Servo Applications
• High Current Drivers Can Control External 3–Phase MOSFET Bridge
• Cycle–By–Cycle Current Limiting
• Pinned–Out Current Sense Reference
• Internal Thermal Shutdown
• Selectable 60°/300° or 120°/240° Sensor Phasings
• Can Efficiently Control Brush DC Motors with External MOSFET
H–Bridge
Device
MC33035DW
MC33035P
ORDERING INFORMATION
Operating
Temperature Range
TA = – 40° to + 85°C
Package
SO–24L
Plastic DIP
BRUSHLESS DC
MOTOR CONTROLLER
SEMICONDUCTOR
TECHNICAL DATA
P SUFFIX
PLASTIC PACKAGE
CASE 724
24
1
DW SUFFIX
PLASTIC PACKAGE
CASE 751E
(SO–24L)
24
1
PIN CONNECTIONS
Top Drive
Output
BT 1
AT 2
Fwd/Rev 3
Sensor
Inputs
SA 4
SB 5
SC 6
Output Enable 7
Reference Output 8
Current Sense
Noninverting Input
9
Oscillator 10
Error Amp
Noninverting Input
Error Amp
Inverting Input
11
12
24 CT
23 Brake
22 60°/120° Select
21 AB
20 BB
19 CB
Bottom
Drive
Outputs
18 VC
17 VCC
16 Gnd
15
Current Sense
Inverting Input
14 Fault Output
13
Error Amp Out/
PWM Input
(Top View)
MOTOROLA ANALOG IC DEVICE DATA
© Motorola, Inc. 1996
Rev 2
1
1 page  
MC33035
Figure 1. Oscillator Frequency versus
Timing Resistor
100
VCC = 20 V
VC = 20 V
TA = 25°C
10
Figure 2. Oscillator Frequency Change
versus Temperature
4.0
VCC = 20 V
VC = 20 V
2.0
RT = 4.7 k
CT = 10 nF
0
CT = 100 nF
0
1.0
CT = 10 nF
CT = 1.0 nF
10 100
RT, TIMING RESISTOR (kΩ)
1000
– 2.0
– 4.0
– 55 – 25 0 25 50 75 100 125
TA, AMBIENT TEMPERATURE (°C)
Figure 3. Error Amp Open Loop Gain and
Phase versus Frequency
56 40
48 60
40
Phase
80
32 100
24
16
8.0
0
– 8.0
–16
– 24
1.0 k
VCC = 20 V
VC = 20 V
VO = 3.0 V
RL = 15 k
CL = 100 pF
TA = 25°C
10 k
Gain
100 k
1.0 M
120
140
160
180
200
220
240
10 M
f, FREQUENCY (Hz)
Figure 4. Error Amp Output Saturation
Voltage versus Load Current
0
Vref
– 0.8 Source Saturation
(Load to Ground)
VCC = 20 V
VC = 20 V
TA = 25°C
–1.6
1.6
0.8
Gnd
Sink Saturation
(Load to Vref)
0
0 1.0 2.0 3.0 4.0 5.0
IO, OUTPUT LOAD CURRENT (mA)
Figure 5. Error Amp Small–Signal
Transient Response
AV = +1.0
3.05
No Load
TA = 25°C
3.0
2.95
1.0 µs/DIV
Figure 6. Error Amp Large–Signal
Transient Response
AV = +1.0
4.5
No Load
TA = 25°C
3.0
1.5
5.0 µs/DIV
MOTOROLA ANALOG IC DEVICE DATA
5
5 Page 
MC33035
Reference
The on–chip 6.25 V regulator (Pin 8) provides charging
current for the oscillator timing capacitor, a reference for the
error amplifier, and can supply 20 mA of current suitable for
directly powering sensors in low voltage applications. In
higher voltage applications, it may become necessary to
transfer the power dissipated by the regulator off the IC. This
is easily accomplished with the addition of an external pass
transistor as shown in Figure 22. A 6.25 V reference level
was chosen to allow implementation of the simpler NPN
circuit, where Vref – VBE exceeds the minimum voltage
required by Hall Effect sensors over temperature. With
proper transistor selection and adequate heatsinking, up to
one amp of load current can be obtained.
Figure 22. Reference Output Buffers
17
Vin
18
UVLO
MPS
U01A
8
To
Sensor
Power
≈ 5.6 V
Control
Circuitry
6.25 V
REF
Vin 39
17
UVLO
18
MPS
U51A
REF
0.1 8
To Control Circuitry
and Sensor Power
6.25 V
The NPN circuit is recommended for powering Hall or opto sensors, where the
output voltage temperature coefficient is not critical. The PNP circuit is slightly
more complex, but is also more accurate over temperature. Neither circuit has
current limiting.
Undervoltage Lockout
A triple Undervoltage Lockout has been incorporated to
prevent damage to the IC and the external power switch
transistors. Under low power supply conditions, it guarantees
that the IC and sensors are fully functional, and that there is
sufficient bottom drive output voltage. The positive power
supplies to the IC (VCC) and the bottom drives (VC) are each
monitored by separate comparators that have their
thresholds at 9.1 V. This level ensures sufficient gate drive
necessary to attain low RDS(on) when driving standard power
MOSFET devices. When directly powering the Hall sensors
from the reference, improper sensor operation can result if
the reference output voltage falls below 4.5 V. A third
comparator is used to detect this condition. If one or more of
the comparators detects an undervoltage condition, the Fault
Output is activated, the top drives are turned off and the
bottom drive outputs are held in a low state. Each of the
comparators contain hysteresis to prevent oscillations when
crossing their respective thresholds.
Fault Output
The open collector Fault Output (Pin 14) was designed to
provide diagnostic information in the event of a system
malfunction. It has a sink current capability of 16 mA and
can directly drive a light emitting diode for visual indication.
Additionally, it is easily interfaced with TTL/CMOS logic for
use in a microprocessor controlled system. The Fault
Output is active low when one or more of the following
conditions occur:
1) Invalid Sensor Input code
2) Output Enable at logic [0]
3) Current Sense Input greater than 100 mV
4) Undervoltage Lockout, activation of one or more of
the comparators
5) Thermal Shutdown, maximum junction temperature
being exceeded
This unique output can also be used to distinguish
between motor start–up or sustained operation in an
overloaded condition. With the addition of an RC network
between the Fault Output and the enable input, it is possible
to create a time–delayed latched shutdown for overcurrent.
The added circuitry shown in Figure 23 makes easy starting
of motor systems which have high inertial loads by providing
additional starting torque, while still preserving overcurrent
protection. This task is accomplished by setting the current
limit to a higher than nominal value for a predetermined time.
During an excessively long overcurrent condition, capacitor
CDLY will charge, causing the enable input to cross its
threshold to a low state. A latch is then formed by the positive
feedback loop from the Fault Output to the Output Enable.
Once set, by the Current Sense Input, it can only be reset by
shorting CDLY or cycling the power supplies.
Drive Outputs
The three top drive outputs (Pins 1, 2, 24) are open
collector NPN transistors capable of sinking 50 mA with a
minimum breakdown of 30 V. Interfacing into higher voltage
applications is easily accomplished with the circuits shown in
Figures 24 and 25.
The three totem pole bottom drive outputs (Pins 19, 20,
21) are particularly suited for direct drive of N–Channel
MOSFETs or NPN bipolar transistors (Figures 26, 27, 28
and 29). Each output is capable of sourcing and sinking up
to 100 mA. Power for the bottom drives is supplied from VC
(Pin 18). This separate supply input allows the designer
added flexibility in tailoring the drive voltage, independent of
VCC. A zener clamp should be connected to this input when
driving power MOSFETs in systems where VCC is greater
than 20 V so as to prevent rupture of the MOSFET gates.
The control circuitry ground (Pin 16) and current sense
inverting input (Pin 15) must return on separate paths to the
central input source ground.
Thermal Shutdown
Internal thermal shutdown circuitry is provided to protect
the IC in the event the maximum junction temperature is
exceeded. When activated, typically at 170°C, the IC acts
as though the Output Enable was grounded.
MOTOROLA ANALOG IC DEVICE DATA
11
11 Page | ||
| Páginas | Total 24 Páginas | |
| PDF Descargar | [ Datasheet MC33035.PDF ] | |
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