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PDF AAT1143 Data sheet ( Hoja de datos )
| Número de pieza | AAT1143 | |
| Descripción | 1MHz 400mA Step-Down Converter | |
| Fabricantes | Advanced Analogic Technologies | |
| Logotipo |  |
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General Description
The AAT1143 SwitchReg™ is a member of
AnalogicTech's Total Power Management IC™
(TPMIC™) product family. It is a 1MHz step-down
converter with an input voltage range of 2.7V to
5.5V and output as low as 0.6V. Its low supply cur-
rent, small size, and high switching frequency
make the AAT1143 the ideal choice for portable
applications.
The AAT1143 is available in either a fixed version
with internal feedback or a programmable version
with external feedback resistors. It can deliver
400mA of load current while maintaining a low
25µA no load quiescent current. The 1MHz switch-
ing frequency minimizes the size of external com-
ponents while keeping switching losses low. The
AAT1143 feedback and control delivers excellent
load regulation and transient response with a small
output inductor and capacitor.
The AAT1143 is designed to maintain high efficien-
cy throughout the operating range, which is critical
for portable applications.
The AAT1143 is available in a space-saving
2.0x2.1mm SC70JW-8 package and is rated over
the -40°C to +85°C temperature range.
AAT1143
1MHz 400mA Step-Down Converter
Features
SwitchReg™
• VIN Range: 2.7V to 5.5V
• VOUT Adjustable Down to 0.6V
— Fixed or Adjustable Version
• 25µA No Load Quiescent Current
• Up to 95% Efficiency
• 400mA Max Output Current
• 1MHz Switching Frequency
• Soft Start
• Over-Temperature Protection
• Current Limit Protection
• 100% Duty Cycle Low-Dropout Operation
• 0.1µA Shutdown Current
• SC70JW-8 Package
• Temperature Range: -40°C to +85°C
Applications
• Cellular Phones
• Digital Cameras
• Handheld Instruments
• Microprocessor / DSP Core / IO Power
• PDAs and Handheld Computers
• USB Devices
Typical Application (Fixed Output Voltage)
VIN
C2
4.7µF
U1
AAT1143
3 VIN
LX 4
1 EN
OUT 2
5 AGND PGND 7
8 PGND PGND 6
L1
4.7µH
VO
C1
4.7µF
AAT1143 Efficiency
(VOUT = 2.5V; L = 4.7µH)
100
VIN = 3.3V
90
80
70
60
0.1
1
10 100
Output Current (mA)
1000
1143.2005.09.1.7
1
1 page  
Typical Characteristics
Efficiency vs. Load
(VOUT = 2.5V; L = 4.7µH)
100
VIN = 3.0V VIN = 3.3V
90
80 VIN = 3.6V
70
60
0.1
1
10 100
Output Current (mA)
AAT1143
1MHz 400mA Step-Down Converter
1000
2.0
1.0
0.0
-1.0
-2.0
0.1
Load Regulation
(VOUT = 2.5V; L = 4.7µH)
VIN = 3.0V
VIN = 3.3V
VIN = 3.6V
1 10 100
Output Current (mA)
1000
Efficiency vs. Load
(VOUT = 1.8V; L = 4.7µH)
100
90 VIN = 2.7V
VIN = 3.6V
80
70 VIN = 4.2V
60
2.0
1.0
0.0
-1.0
50
0.1
1 10 100
Output Current (mA)
1000
-2.0
0.1
DC Regulation
(VOUT = 1.8V; L = 4.7µH)
VIN = 4.2V
VIN = 2.7V
VIN = 3.6V
1 10 100
Output Current (mA)
1000
Frequency vs. Input Voltage
(VOUT = 1.8V)
1.0
Output Voltage Error vs. Temperature
(VIN = 3.6V; VO = 1.5V)
2.0
0.5
1.0
0.0
-0.5
INTERNAL DO0.0 CUMENT
-1.0
-1.0
DO NOT COPY-1.5
-2.0 -2.0
2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5
-40 -20 0 20 40 60 80 100
Input Voltage (V)
Temperature (°C)
1143.2005.09.1.7
5
5 Page 
AAT1143
1MHz 400mA Step-Down Converter
The maximum input capacitor RMS current is:
IRMS = IO ·
VO · ⎛1 - VO ⎞
VIN ⎝ VIN ⎠
The input capacitor RMS ripple current varies with
the input and output voltage and will always be less
than or equal to half of the total DC load current.
VO
VIN
· ⎛⎝1 -
VO ⎞
VIN ⎠
=
D · (1 - D) =
0.52 = 1
2
for VIN = 2 x VO
I =RMS(MAX)
IO
2
The term
VO
VIN
·
⎛⎝1
-
VO ⎞
VIN ⎠
appears in both the input
voltage ripple and input capacitor RMS current
equations and is a maximum when VO is twice VIN.
This is why the input voltage ripple and the input
capacitor RMS current ripple are a maximum at
50% duty cycle.
The input capacitor provides a low impedance loop
for the edges of pulsed current drawn by the
AAT1143. Low ESR/ESL X7R and X5R ceramic
capacitors are ideal for this function. To minimize
stray inductance, the capacitor should be placed as
closely as possible to the IC. This keeps the high
frequency content of the input current localized,
minimizing EMI and input voltage ripple.
The proper placement of the input capacitor (C2)
can be seen in the evaluation board layout in
Figure 2.
A laboratory test set-up typically consists of two
long wires running from the bench power supply to
the evaluation board input voltage pins. The induc-
tance of these wires, along with the low-ESR
ceramic input capacitor, can create a high Q net-
work that may affect converter performance. This
problem often becomes apparent in the form of
excessive ringing in the output voltage during load
transients. Errors in the loop phase and gain meas-
urements can also result.
Since the inductance of a short PCB trace feeding
the input voltage is significantly lower than the
power leads from the bench power supply, most
applications do not exhibit this problem.
In applications where the input power source lead
inductance cannot be reduced to a level that does
not affect the converter performance, a high ESR
tantalum or aluminum electrolytic should be placed
in parallel with the low ESR, ESL bypass ceramic.
This dampens the high Q network and stabilizes
the system.
Output Capacitor
The output capacitor limits the output ripple and
provides holdup during large load transitions. A
4.7µF to 10µF X5R or X7R ceramic capacitor typi-
cally provides sufficient bulk capacitance to stabi-
lize the output during large load transitions and has
the ESR and ESL characteristics necessary for low
output ripple.
The output voltage droop due to a load transient is
dominated by the capacitance of the ceramic out-
put capacitor. During a step increase in load cur-
rent, the ceramic output capacitor alone supplies
the load current until the loop responds. Within two
or three switching cycles, the loop responds and
the inductor current increases to match the load
current demand. The relationship of the output volt-
age droop during the three switching cycles to the
output capacitance can be estimated by:
COUT
=
3 · ∆ILOAD
VDROOP · FS
Once the average inductor current increases to the
DC load level, the output voltage recovers. The
above equation establishes a limit on the minimum
value for the output capacitor with respect to load
transients.
The internal voltage loop compensation also limits
the minimum output capacitor value to 4.7µF. This
is due to its effect on the loop crossover frequency
(bandwidth), phase margin, and gain margin.
Increased output capacitance will reduce the
crossover frequency with greater phase margin.
1143.2005.09.1.7
11
11 Page | ||
| Páginas | Total 20 Páginas | |
| PDF Descargar | [ Datasheet AAT1143.PDF ] | |
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