PDF MC33215 Data sheet ( Hoja de datos )

Número de pieza	MC33215
Descripción	Telephone Line Interface and Speakerphone Circuit
Fabricantes	Motorola Semiconductors
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No Preview Available ! Order this document by MC33215/D MC33215 Advance Information Telephone Line Interface and Speakerphone Circuit The MC33215 is developed for use in fully electronic telephone sets with speakerphone functions. The circuit performs the ac and dc line termination, 2–4 wire conversion, line length AGC and DTMF transmission. The speakerphone part includes a half duplex controller with signal and noise monitoring, base microphone and loudspeaker amplifiers and an efficient supply. The circuit is designed to operate at low line currents down to 4.0 mA enabling parallel operation with a classical telephone set. • Highly Integrated Cost Effective Solution • Straightforward AC and DC Parameter Adjustments • Efficient Supply for Loudspeaker Amplifier and Peripherals • Stabilized Supply Point for Handset Microphone • Stabilized Supply Point for Base Microphone • Loudspeaker Amplifier can be Powered and Used Separately • Smooth Switch–Over from Handset to Speakerphone Operation • Adjustable Switching Depth for Handsfree Operation 52 1 FB SUFFIX PLASTIC PACKAGE CASE 848B (TQFP–52) 42 1 B SUFFIX PLASTIC PACKAGE CASE 858 (SDIP–42) ORDERING INFORMATION Device Operating Temperature Range Package MC33215FB MC33215B TA = –20° to +70°C TQFP–52 SDIP–42 Simplified Application DTMF Handset Microphone Base Microphone VCC or External Supply Base Loudspeaker MF HM BM LS AC Impedance Attenuator Duplex Controller Attenuator DC Offset Line Current Current Splitter 1:10 Line Driver VCC Supply DC Slope Telephone Line Receive Signal Rx Handset Earpiece Auxiliary Input This device contains 2782 active transistors. This document contains information on a new product. Specifications and information herein arMe OsuTbjOecRt tOo cLhAangAeNwAithLoOut GnotIiCce.DEVICE DATA © Motorola, Inc. 1997 Rev 0 1 1 page MC33215 ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz, PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.) Characteristic Min Typ Max Unit ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁRx CHANNEL, LOUDSPEAKER PRE–AMPLIFIER (SPS = HIGH, Rx MODE FORCED) ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVoltage Gain from VRXI to VRLS (Note 2) Vline = 20 mVrms 21 24 27 dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁGain Reduction in Mute Condition 60 – – dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁSPS = Low or MUT = Low ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁRx CHANNEL, LOUDSPEAKER AMPLIFIER ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVoltage Gain from VLSIto VLSP VLSI = 10 mVrms ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁAttenuation at Delta RVOL= 47 kΩ 25 26 27 dB – 32 – dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁPsophometrically Weighted Noise Level at VLSP ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁRXI Shorted to Gnd via 10 µF – 1.2 – mVrms ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁConfidence Level During DTMF Dialing ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVMF = 7.5 mVrms MUT = Low Available Peak Current from LSO 150 200 250 mVrms 110 – – mApeak ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁOutput Capability into 25 Ω ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁTHD ≤2%, VLSI = 55 mVrms ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁOutput Capability into 25 Ω ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁTHD ≤2%, VLS= 5.0 V, VLSI = 90 mVrms Gain Reduction in Mute Condition ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁLSM = Low 1.8 – 2.7 – 60 – – Vpp – Vpp – dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁRx CHANNEL PEAK–TO–PEAK LIMITER ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁPeak–to–Peak Limiter Attack Time ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVLSI Jumps from 40 mVrms to 120 mVrms ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁPeak–to–Peak Limiter Release Time VLSI Jumps from 120 mVrms to 40 mVrms ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁTHD at 10 dB Overdrive ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVLSI = 120 mVrms ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁPeak–to–Peak Limiter Disable Threshold at PPL – – 5.0 ms – 300 – ms – – 7.0 % – – 0.1 V ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁAUTOMATIC GAIN CONTROL ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁGain Reduction in Transmit and Receive Channel with Respect to Iline = 18 mA 4.5 6.0 7.5 dB Iline = 70 mA ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁGain Variation in Transmit and Receive Channel with Respect to Iline =18 mA with ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁAGC Disabled (AGC to VDD) – – 1.5 dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁHighest Line Current for Maximum Gain – 20 – mA ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁLowest Line Current for Minimum Gain – 50 – mA ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁBALANCE RETURN LOSS ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁBalance Return Loss with Respect to 600 Ω 20 – – dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁSIDETONE ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVoltageGainfromVHM to VEAR S1 in Position 2 – – 28 dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁLOGARITHMIC AMPLIFIERS AND ENVELOPE DETECTORS ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVoltage Gain from RXI to RSA 18 20 22 dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVRXI = 15 mVrms ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVoltage Gain from BMI to TSA ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVBM = 0.5 mVrms 17.5 18.5 19.5 dB Dynamic Range of Logarithmic Compression from TSA to TSE and RSA to RSE ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁITSA and IRSA from 2.5 µA to 250 µA 40 – – dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁEnvelope Tracking Between TSE and RSE and Between TBN and RBN – ±3.0 – dB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁMaximum Source Current from TSE or RSE 0.3 0.4 0.5 µA NOTE: 2. Corresponding to –0.6 dB gain from the line to output RLS in the typical application. MOTOROLA ANALOG IC DEVICE DATA 5 5 Page MC33215 RXI. A second high pass filtering is introduced by the combination of CGRX and RGRX. A low pass filter is created by CRXO and RRXO. The coupling capacitor at the output RXO is not used for setting a high pass filter but merely for dc decoupling. In combination with dynamic ear capsules, the EAR amplifier can become unstable due to the highly inductive characteristic of some of the capsules. To regain stability, a 100 nF capacitor can be connected from RXS to Gnd in those cases. An additional 10 nF at the RXI input, as shown in the typical application, improves the noise figure of the receiver stage. Sidetone Cancellation The line driver and the receiver amplifier of the MC33215 are tied up in a bridge configuration as depicted in Figure 7. This bridge configuration performs the so–called hybrid function which, in the ideal case, prevents transmitted signals from entering the receive channel. Automatic Gain Control To obtain more or less constant signal levels for transmit and receive regardless of the telephone line length, both the transmit and receive gain can be varied as a function of line current when the AGC feature is used. The gain reduction as a function of line current, and thus line length, is depicted in Figure 8. Figure 8. Automatic Gain Control 0 –1.0 RAGC = 20 k –2.0 RAGC = 30 k –3.0 –4.0 –5.0 Figure 7. Sidetone Bridge VLN Zline//Zset Gnd RSLP/11 Transmit ńVHM x 15 RSLP 11 Zbal RXI Receive RSLB Gnd SLP As can be seen from Figure 7 by inspection, the receiver will not pick up any transmit signal when the bridge is in balance, that is to say when: ńńZbal + ńRSLB Zline Zset RSLP 11 The sidetone suppression is normally measured in an acoustic way. The signal at the earpiece when applying a signal on the microphone is compared with the signal at the earpiece when applying a signal on the line. The suppression takes into account the transmit and receive gains set. In fact the sidetone suppression can be given as a purely electrical parameter given by the properties of the sidetone bridge itself. For the MC33215, this so–called electrical sidetone suppression ASTE can be given as: + ńńńASTE 1 – Zbal RSLB x RSLP 11 Zline Zset Values of –12 dB or better, thus ASTE < 0.25, can easily be reached in this way. –6.0 0 10 20 30 40 50 60 70 Iline (mA) For small line currents, and thus long lines, no gain reduction is applied and thus the transmit and receive gains are at their maximum. For line currents higher than Istart, the gain is gradually reduced until a line current Istop is reached. This should be the equivalent of a very short line, and the gain reduction equals 6.0 dB. For higher line currents the gain is not reduced further. For the start and stop currents the following relations are valid: + ńIstop 1 RSLP 11 + ń ńIstart 1 – 20 µ x RAGC RSLP 11 RSLP 11 For the typical application, where RAGC = 30 kΩ, the gain will start to be reduced at Istart = 20 mA while reaching 6.0 dB of gain reduction at Istop = 50 mA. When AGC is connected to VDD, the AGC function is disabled leading to no gain reduction for any line current. This is also sometimes called PABX mode. The automatic gain control takes effect in the HMIC and Rx amplifiers as well as in the BMIC amplifier. In this way the AGC is also active in speakerphone mode, see the handsfree operation paragraph. Privacy and DTMF Mode During handset operation a privacy and a DTMF mode can be entered according the logic Table 1. Table 1. Logic Table for Handset Mode Logic Inputs SPS MUT PRS ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ0 1 1 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ0 1 0 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ0 0 X Mode Handset Normal Handset Privacy Handset DTMF HMIC On Off Off BMIC Off Off Off Amplifiers DTMF Off Rx On On On On Off RXatt Off Off Off EAR On On On MOTOROLA ANALOG IC DEVICE DATA 11 11 Page

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