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PA243 데이터시트 PDF




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부품번호 PA243 기능
기능 High Voltage Power Operational Amplifier
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PA243 데이터시트, 핀배열, 회로
P r o dPu cAt I2Inn4nn3oovvaa t i o n FFrroomm
PAP2A42433
High Voltage Power Operational Amplifier
FEATURES
• RoHS COMPLIANT
• SURFACE MOUNT PACKAGE
• MONOLITHIC MOS TECHNOLOGY
• LOW COST
• HIGH VOLTAGE OPERATION—350V
• LOW QUIESCENT CURRENT TYP.—2.2mA
• NO SECOND BREAKDOWN
• HIGH OUTPUT CURRENT—120 mA PEAK
APPLICATIONS
• TELEPHONE RING GENERATOR
• PIEZO ELECTRIC POSITIONING
• ELECTROSTATIC TRANSDUCER & DEFLECTION
• DEFORMABLE MIRROR FOCUSING
DESCRIPTION
The PA243 is a dual high voltage monolithic MOSFET op-
erational amplifier achieving performance features previously
found only in hybrid designs while increasing reliability. This
approach provides a cost-effective solution to applications
where multiple amplifiers are required. Inputs are protected
from excessive common mode and differential mode volt-
ages. The safe operating area (SOA) has no secondary
breakdown limitations and can be observed with all type
loads by choosing an appropriate current limiting resistor.
External compensation provides the user flexibility in choosing
optimum gain and bandwidth for the application.
The PA243DF is packaged in a 24 pin PSOP (JEDEC
MO-166) package. The heatslug of the PA243DF package is
isolated in excess of full supply voltage.
TYPICAL APPLICATION
R 20R
VIN +175
20R
20R
+175
A
PA243
10pF
10pF
R CL
R CL
47
PIEZO
TRANSDUCER
47
B
PA243
–175
–175
RN
CN
Low Cost 660v p-p Piezo Drive
A single PA243 amplifier operates as a bridge driver for a piezo
transducer providing a low cost 660 volt total drive capability.
The RN CN network serves to raise the apparent gain of A2 at
high frequencies. If RN is set equal to R the amplifiers can be
compensated identically and will have matching bandwidths.
See application note 20 for more details.
24-pin PSOP
PACKAGE STYLE DF
EQUIVALENT SCHEMATIC (one of two channels)
Q1 Q2
+VS
CC1
CC2
+IN
-IN
D1
Q7
Q8
D4
Q3
Q5 Q6
Q10
Q9
Q4
ILIM
OUT
D2 Q11
D3
Q13
Q12 Q14
Q15
D5
EXTERNAL CONNECTIONS
-VS
* +Vsa
NC
La
COMPa
RCL COMPa
CC OUTa
NC
-INb
+INb
1
* -Vsb
+
A
-
B
24
-Vsa
*
NC
NC
+INa
-INa
NC
OUTb
COMPb
COMPb
ILb
CC
RCL
NC
+Vsb
*
For CC values, see graph on page 3.
Note: CC must be rated for full supply voltage.
* Supply bypassing required. See general Operating Con-
siderations.
PA24h3tUtp://www.cirrus.com
Copyright © Cirrus Logic, Inc. 2009
(All Rights Reserved)
APEX − PA24M3AUYR2E0V0G91




PA243 pdf, 반도체, 판매, 대치품
PA243
Product Innova tionFrom
GENERAL
Please read Application Note 1 "General Operating Consid-
erations" which covers stability, power supplies, heat sinking,
mounting, current limit, SOA interpretation, and specification
interpretation. Visit www.Cirrus.com for design tools that help
automate tasks such as calculations for stability, internal power
dissipation, current limit, heat sink selection, Apex Precision
Power's complete Application Notes library, Technical Seminar
Workbook and Evaluation Kits.
PHASE COMPENSATION
Open loop gain and phase shift both increase with increas-
ing temperature. The PHASE COMPENSATION typical graph
shows closed loop gain and phase compensation capacitor
value relationships for four case temperatures.The curves are
based on achieving a phase margin of 50°. Calculate the high-
est case temperature for the application (maximum ambient
temperature and highest internal power dissipation) before
choosing the compensation. Keep in mind that when working
with small values of compensation, parasitics may play a large
role in performance of the finished circuit. The compensation
capacitor must be rated for at least the total voltage applied
to the amplifier and should be a temperature stable type such
as NPO or COG.
OTHER STABILITY CONCERNS
There are two important concepts about closed loop gain
when choosing compensation. They stem from the fact that
while "gain" is the most commonly used term, β (the feedback
factor) is really what counts when designing for stability.
1. Gain must be calculated as a non-inverting circuit (equal
input and feedback resistors can provide a signal gain of
-1, but for calculating offset errors, noise, and stability, this
is a gain of 2).
2. Including a feedback capacitor changes the feedback factor
or gain of the circuit. Consider Rin=4.7k, Rf=47k for a gain
of 11. Compensation of 4.7 to 6.8pF would be reasonable.
Adding 33pF parallel to the 47k rolls off the circuit at 103kHz,
and at 2MHz has reduced gain from 11 to roughly 1.5 and
the circuit is likely to oscillate.
As a general rule the DC summing junction impedance
(parallel combination of the feedback resistor and all input
resistors) should be limited to 5k ohms or less. The amplifier
input capacitance of about 6pF, plus capacitance of connecting
traces or wires and (if used) a socket will cause undesirable
circuit performance and even oscillation if these resistances
are too high. In circuits requiring high resistances, measure or
estimate the total sum point capacitance, multiply by Rin/Rf, and
parallel Rf with this value. Capacitors included for this purpose
are usually in the single digit pF range. This technique results
in equal feedback factor calculations for AC and DC cases. It
does not produce a roll off, but merely keeps β constant over
a wide frequency range. Paragraph 6 of Application Note 19
details suitable stability tests for the finished circuit.
CURRENT LIMIT
For proper operation, the current limit resistor, Rcl, must be
connected as shown in the external connection diagram. The
minimum value is 3.9 ohms, however for optimum reliability,
the resistor should be set as high as possible. The maximum
practical value is 110 ohms. Current limit values can be pre-
dicted as follows:
Ilimit
=
Vbe
Rcl
Where Vbe is shown in the CURRENT LIMIT typical
graph.
Note that +Vbe should be used to predict current through
the +Vs pin, -Vbe for current through the -Vs pin, and that they
vary with case temperature. Value of the current limit resistor
at a case temperature of 25° can be estimated as follows:
Rcl
=
0.7
Ilimit
When the amplifier is current limiting, there may be spurious
oscillation present during the current limited portion of the nega-
tive half cycle.The frequency of the oscillation is not predictable
and depends on the compensation, gain of the amplifier, value
of the current limit resistor, and the load. The oscillation will
cease as the amplifier comes out of current limit.
SAFE OPERATING AREA
The MOSFET output stage of the PA243 is not limited by
second breakdown considerations as in bipolar output stages.
However there are still three distinct limitations:
1. Voltage withstand capability of the transistors.
2. Current handling capability of the die metalization.
3. Temperature of the output MOSFETS.
PA243 SOA
200
120
100
3002m0S0mS
50
40
30
20
10
DC,
T
C
D=C1,2T5C°C= D8C5°C
5
4
3 PULSE CURVES @
10% DUTY CYCLE MAX.
2
10 20 30 50 100
200 300 500
SUPPLY TO OUTPUT DIFFERENTIAL, VS- VO (V)
4 PA243U

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